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1 lt1632/lt1633 sn1632 16323fs 45mhz, 45v/ m s, dual/quad rail-to-rail input and output precision op amps features n gain-bandwidth product: 45mhz n slew rate: 45v/ m s n low supply current per amplifier: 4.3ma n input common mode range includes both rails n output swings rail-to-rail n input offset voltage, rail-to-rail: 1350 m v max n input offset current: 440na max n input bias current: 2.2 m a max n open-loop gain: 800v/mv min n low input noise voltage: 12nv/ ? hz typ n low distortion: C 92dbc at 100khz n wide supply range: 2.7v to 15v n large output drive current: 35ma min n dual in 8-pin pdip and so packages the lt ? 1632/lt1633 are dual/quad, rail-to-rail input and output op amps with a 45mhz gain-bandwidth product and a 45v/ m s slew rate. the lt1632/lt1633 have excellent dc precision over the full range of operation. input offset voltage is typically less than 400 m v and the minimum open-loop gain of 0.8 million into a 10k load virtually eliminates all gain error. common mode rejection is typically 83db over the full rail- to-rail input range when on a single 5v supply for excellent noninverting performance. the lt1632/lt1633 maintain their performance for sup- plies from 2.7v to 36v and are specified at 3v, 5v and 15v supplies. the inputs can be driven beyond the supplies without damage or phase reversal of the output. the output delivers load currents in excess of 35ma. the lt1632 is available in 8-pin pdip and so packages with the standard dual op amp pinout. the lt1633 features the standard quad op amp configuration and is available in a 14-pin plastic so package. these devices can be used as plug-in replacements for many standard op amps to improve input/output range and performance. descriptio n u applicatio n s u n active filters n rail-to-rail buffer amplifiers n driving a/d converters n low voltage signal processing n battery-powered systems , ltc and lt are registered trademarks of linear technology corporation. frequency (hz) voltage gain (db) 50 40 30 20 10 0 ?0 ?0 ?0 ?0 ?0 ?0 ?0 100 10k 100k 10m 1632/33 ta02 1k 1m common mode input differential input v s = 3v a v = 100 typical applicatio n u single supply, 40db gain, 550khz instrumentation amplifier + 1/2 lt1632 v in v in + v out 1630/31 f02 r1 20k r2 2k r4 20k r5 432 r3 2k + 1/2 lt1632 3v frequency response
2 lt1632/lt1633 sn1632 16323fs absolute m axi m u m ratings w ww u total supply voltage (v + to v C ) ............................. 36v input current ..................................................... 10ma output short-circuit duration (note 2) ........ continuous operating temperature range ................ C 40 c to 85 c specified temperature range (note 4) ..... C 40 c to 85 c junction temperature .......................................... 150 c storage temperature range ................. C 65 c to 150 c lead temperature (soldering, 10 sec).................. 300 c consult factory for military and industrial grade parts. package/order i n for m atio n w u u order part number lt1632cn8 lt1632cs8 lt1632in8 lt1632is8 order part number t jmax = 150 c, q ja = 150 c/ w t jmax = 150 c, q ja = 130 c/ w (n8) t jmax = 150 c, q ja = 190 c/ w (s8) lt1633cs lt1633is s8 part marking 1 2 3 4 8 7 6 5 top view out a in a + in a v v + out b in b + in b s8 package 8-lead plastic so n8 package 8-lead pdip a b 1632 1632i top view s package 14-lead plastic so 1 2 3 4 5 6 7 14 13 12 11 10 9 8 outa in a + in a v + + in b in b out b out d in d + in d v + in c in c out c a d b c electrical characteristics symbol parameter conditions min typ max units v os input offset voltage v cm = v + 400 1350 m v v cm = v C 400 1350 m v d v os input offset shift v cm = v C to v + 350 1500 m v input offset voltage match (channel-to-channel) v cm = v C , v + (note 5) 500 2300 m v i b input bias current v cm = v + 0 1.15 2.2 m a v cm = v C C 2.2 C 1.15 0 m a d i b input bias current shift v cm = v C to v + 2.3 4.4 m a input bias current match (channel-to-channel) v cm = v + (note 5) 50 880 na v cm = v C (note 5) 50 880 na i os input offset current v cm = v + 40 440 na v cm = v C 40 440 na d i os input offset current shift v cm = v C to v + 80 880 na input noise voltage 0.1hz to 10hz 400 nv p-p e n input noise voltage density f = 1khz 12 nv/ ? hz i n input noise current density f = 1khz 1.6 pa/ ? hz c in input capacitance 5pf a vol large-signal voltage gain v s = 5v, v o = 300mv to 4.7v, r l = 10k 450 2000 v/mv v s = 3v, v o = 300mv to 2.7v, r l = 10k 350 1500 v/mv cmrr common mode rejection ratio v s = 5v, v cm = v C to v + 70 83 db v s = 3v, v cm = v C to v + 66 81 db t a = 25 c, v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted. (note 1)
3 lt1632/lt1633 sn1632 16323fs electrical characteristics t a = 25 c, v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted. symbol parameter conditions min typ max units cmrr match (channel-to-channel) (note 5) v s = 5v, v cm = v C to v + 65 85 db v s = 3v, v cm = v C to v + 61 82 db psrr power supply rejection ratio v s = 2.7v to 12v, v cm = v o = 0.5v 82 100 db psrr match (channel-to-channel) (note 5) v s = 2.7v to 12v, v cm = v o = 0.5v 79 101 db minimum supply voltage (note 9) v cm = v o = 0.5v 2.6 2.7 v v ol output voltage swing low (note 6) no load 15 30 mv i sink = 0.5ma 32 60 mv i sink = 25ma, v s = 5v 600 1200 mv i sink = 20ma, v s = 3v 500 1000 mv v oh output voltage swing high (note 6) no load 16 40 mv i source = 0.5ma 42 80 mv i source = 20ma, v s = 5v 910 1800 mv i source = 15ma, v s = 3v 680 1400 mv i sc short-circuit current v s = 5v 20 40 ma v s = 3v 15 30 ma i s supply current per amplifier 4.3 5.2 ma gbw gain-bandwidth product (note 7) f = 100khz 22 45 mhz sr slew rate (note 8) v s = 5v, a v = C 1, r l = open, v o = 4v 13 27 v/ m s v s = 3v, a v = C 1, r l = open 11 22 v/ m s t s settling time v s = 5v, a v = 1, r l = 1k, 400 ns 0.01%, v step = 2v symbol parameter conditions min typ max units v os input offset voltage v cm = v + C 0.1v l 600 2000 m v v cm = v C + 0.2v l 600 2000 m v v os tc input offset voltage drift (note 3) l 815 m v/ c v cm = v + C 0.1v l 2.5 7 m v/ c d v os input offset voltage shift v cm = v C + 0.2v to v + C 0.1v l 400 2300 m v input offset voltage match (channel-to-channel) v cm = v C + 0.2v, v + C 0.1v (note 5) l 700 3750 m v i b input bias current v cm = v + C 0.1v l 0 1.3 2.6 m a v cm = v C + 0.2v l C 2.6 C 1.3 0 m a d i b input bias current shift v cm = v C + 0.2v to v + C 0.1v l 2.6 5.2 m a input bias current match (channel-to-channel) v cm = v + C 0.1v (note 5) l 50 1040 na v cm = v C + 0.2v (note 5) l 50 1040 na i os input offset current v cm = v + C 0.1v l 40 520 na v cm = v C + 0.2v l 40 520 na d i os input offset current shift v cm = v C + 0.2v to v + C 0.1v l 80 1040 na a vol large-signal voltage gain v s = 5v, v o = 300mv to 4.7v, r l = 10k l 300 1100 v/mv v s = 3v, v o = 300mv to 2.7v, r l = 10k l 200 1000 v/mv cmrr common mode rejection ratio v s = 5v, v cm = v C + 0.2v to v + C 0.1v l 67 81 db v s = 3v, v cm = v C + 0.2v to v + C 0.1v l 61 77 db cmrr match (channel-to-channel) (note 5) v s = 5v, v cm = v C + 0.2v to v + C 0.1v l 62 78 db v s = 3v, v cm = v C + 0.2v to v + C 0.1v l 57 73 db psrr power supply rejection ratio v s = 3v to 12v, v cm = v o = 0.5v l 81 94 db psrr match (channel-to-channel) (note 5) v s = 3v to 12v, v cm = v o = 0.5v l 77 95 db 0 c < t a < 70 c, v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted.
4 lt1632/lt1633 sn1632 16323fs electrical characteristics symbol parameter conditions min typ max units v os input offset voltage v cm = v + C 0.1v l 700 2400 m v v cm = v C + 0.2v l 700 2400 m v v os tc input offset voltage drift (note 3) l 815 m v/ c v cm = v + C 0.1v l 2.5 7 m v/ c d v os input offset voltage shift v cm = v C + 0.2v to v + C 0.1v l 475 2500 m v input offset voltage match (channel-to-channel) v cm = v C + 0.2v, v + (note 5) l 750 4000 m v i b input bias current v cm = v + C 0.1v l 0 1.46 3.0 m a v cm = v C + 0.2v l C 3.0 C 1.46 0 m a d i b input bias current shift v cm = v C + 0.2v to v + C 0.1v l 2.92 6.0 m a input bias current match (channel-to-channel) v cm = v + C 0.1v (note 5) l 70 1160 na v cm = v C + 0.2v (note 5) l 70 1160 na i os input offset current v cm = v + C 0.1v l 75 580 na v cm = v C + 0.2v l 75 580 na d i os input offset current shift v cm = v C + 0.2v to v + C 0.1v l 50 1160 na a vol large-signal voltage gain v s = 5v, v o = 300mv to 4.7v, r l = 10k l 250 1000 v/mv v s = 3v, v o = 300mv to 2.7v, r l = 10k l 200 800 v/mv cmrr common mode rejection ratio v s = 5v, v cm = v C + 0.2v to v + C 0.1v l 65 80 db v s = 3v, v cm = v C + 0.2v to v + C 0.1v l 60 75 db cmrr match (channel-to-channel) (note 5) v s = 5v, v cm = v C + 0.2v to v + C 0.1v l 62 78 db v s = 3v, v cm = v C + 0.2v to v + C 0.1v l 57 73 db psrr power supply rejection ratio v s = 3v to 12v, v cm = v o = 0.5v l 79 95 db psrr match (channel-to-channel) (note 5) v s = 3v to 12v, v cm = v o = 0.5v l 75 95 db minimum supply voltage (note 9) v cm = v o = 0.5v l 2.6 2.7 v v ol output voltage swing low (note 6) no load l 19 40 mv i sink = 0.5ma l 39 80 mv i sink = 25ma, v s = 5v l 730 1500 mv i sink = 20mv, v s = 3v l 580 1200 mv symbol parameter conditions min typ max units minimum supply voltage (note 9) v cm = v o = 0.5v l 2.6 2.7 v v ol output voltage swing low (note 6) no load l 18 40 mv i sink = 0.5ma l 37 80 mv i sink = 25ma, v s = 5v l 700 1400 mv i sink = 20ma, v s = 3v l 560 1200 mv v oh output voltage swing high (note 6) no load l 16 40 mv i source = 0.5ma l 50 100 mv i source = 15ma, v s = 5v l 820 1600 mv i source = 10ma, v s = 3v l 550 1100 mv i sc short-circuit current v s = 5v l 18 37 ma v s = 3v l 13 26 ma i s supply current per amplifier l 4.9 6.0 ma gbw gain-bandwidth product (note 7) f = 100khz l 20 41 mhz sr slew rate (note 8) v s = 5v, a v = C 1, r l = open, v o = 4v l 13 26 v/ m s v s = 3v, a v = C 1, r l = open l 10 21 v/ m s C40 c < t a < 85 c, v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted. (note 4) 0 c < t a < 70 c, v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted.
5 lt1632/lt1633 sn1632 16323fs electrical characteristics C40 c < t a < 85 c, v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted. (note 4) symbol parameter conditions min typ max units v os input offset voltage v cm = v + 500 2200 m v v cm = v C 500 2200 m v d v os input offset voltage shift v cm = v C to v + 360 2200 m v input offset voltage match (channel-to-channel) v cm = v C , v + (note 5) 700 3500 m v i b input bias current v cm = v + 0 1.15 2.2 m a v cm = v C C 2.2 C 1.15 0 m a d i b input bias current shift v cm = v C to v + 2.3 4.4 m a input bias current match (channel-to-channel) v cm = v + (note 5) 50 880 na v cm = v C (note 5) 50 880 na i os input offset current v cm = v + 50 440 na v cm = v C 50 440 na d i os input offset current shift v cm = v C to v + 36 880 na input noise voltage 0.1hz to 10hz 400 nv p-p e n input noise voltage density f = 1khz 12 nv/ ? hz i n input noise current density f = 1khz 1.6 pa/ ? hz c in input capacitance f = 100khz 3 pf a vol large-signal voltage gain v o = C 14.5v to 14.5v, r l = 10k 800 5000 v/mv v o = C 10v to 10v, r l = 2k 400 2500 v/mv channel separation v o = C 10v to 10v, r l = 2k 110 127 db cmrr common mode rejection ratio v cm = v C to v + 82 98 db cmrr match (channel-to-channel) (note 5) v cm = v C to v + 80 101 db psrr power supply rejection ratio v s = 5v to 15v 82 96 db psrr match (channel-to-channel) (note 5) v s = 5v to 15v 80 101 db v ol output voltage swing low (note 6) no load 16 35 mv i sink = 5ma 150 300 mv i sink = 25ma 600 1200 mv v oh output voltage swing high (note 6) no load 16 40 mv i source = 5ma 250 500 mv i source = 25ma 1200 2400 mv symbol parameter conditions min typ max units v oh output voltage swing high (note 6) no load l 16 40 mv i source = 0.5ma l 55 110 mv i source = 15ma, v s = 5v l 860 1700 mv i source = 10ma, v s = 3v l 580 1200 mv i sc short-circuit current v s = 5v l 17 36 ma v s = 3v l 12 24 ma i s supply current per amplifier l 4.95 6.2 ma gbw gain-bandwidth product (note 7) f = 100khz l 20 40 mhz sr slew rate (note 8) v s = 5v, a v = C1, r l = open, v o = 4v l 11 22 v/ m s v s = 3v, a v = C1, r l = open l 918 v/ m s t a = 25 c, v s = 15v, v cm = 0v, v out = 0v, unless otherwise noted.
6 lt1632/lt1633 sn1632 16323fs electrical characteristics t a = 25 c, v s = 15v, v cm = 0v, v out = 0v, unless otherwise noted. symbol parameter conditions min typ max units i sc short-circuit current 35 70 ma i s supply current per amplifier 4.6 6 ma gbw gain-bandwidth product (note 7) f = 100khz 22 45 mhz sr slew rate a v = C 1, r l = open, v o = 10v, 22 45 v/ m s measure at v o = 5v t s settling time 0.01%, v step = 10v, a v = 1, r l = 1k 575 ns symbol parameter conditions min typ max units v os input offset voltage v cm = v + C 0.1v l 800 2750 m v v cm = v C + 0.2v l 800 2750 m v v os tc input offset voltage drift (note 3) l 10 17 m v/ c v cm = v + C 0.1v l 511 m v/ c d v os input offset voltage shift v cm = v C + 0.2v to v + C 0.1v l 500 2500 m v input offset voltage match (channel-to-channel) v cm = v C + 0.2v, v + C 0.1v (note 5) l 800 4000 m v i b input bias current v cm = v + C 0.1v l 0 1.3 2.6 m a v cm = v C + 0.2v l C 2.6 C 1.3 0 m a d i b input bias current shift v cm = v C + 0.2v to v + C 0.1v l 2.6 5.2 m a input bias current match (channel-to-channel) v cm = v + C 0.1v (note 5) l 70 1040 na v cm = v C + 0.2v (note 5) l 70 1040 na i os input offset current v cm = v + C 0.1v l 70 520 na v cm = v C + 0.2v l 70 520 na d i os input offset current shift v cm = v C + 0.2v to v + C 0.1v l 140 1040 na a vol large-signal voltage gain v o = C 14.5v to 14.5v, r l = 10k l 600 4000 v/mv v o = C 10v to 10v, r l = 2k l 300 2000 v/mv channel separation v o = C 10v to 10v, r l = 2k l 110 125 db cmrr common mode rejection ratio v cm = v C + 0.2v to v + C 0.1v l 81 96 db cmrr match (channel-to-channel) (note 5) v cm = v C + 0.2v to v + C 0.1v l 77 95 db psrr power supply rejection ratio v s = 5v to 15v l 80 94 db psrr match (channel-to-channel) (note 5) v s = 5v to 15v l 74 95 db v ol output voltage swing low (note 6) no load l 21 45 mv i sink = 5ma l 180 350 mv i sink = 25ma l 680 1400 mv v oh output voltage swing high (note 6) no load l 15 40 mv i source = 5ma l 300 600 mv i source = 25ma l 1400 2800 mv i sc short-circuit current l 28 57 ma i s supply current per amplifier l 5.2 6.9 ma gbw gain-bandwidth product (note 7) f = 100khz l 20 41 mhz sr slew rate a v = C 1, r l = open, v o = 10v, l 21 43 v/ m s measured at v o = 5v 0 c < t a < 70 c, v s = 15v, v cm = 0v, v out = 0v, unless otherwise noted.
7 lt1632/lt1633 sn1632 16323fs electrical characteristics C40 c < t a < 85 c, v s = 15v, v cm = 0v, v out = 0v, unless otherwise noted. (note 4) symbol parameter conditions min typ max units v os input offset voltage v cm = v + C 0.1v l 1000 3000 m v v cm = v C + 0.2v l 1000 3000 m v v os tc input offset voltage drift (note 3) l 10 17 m v/ c v cm = v + C 0.1v l 511 m v/ c d v os input offset voltage shift v cm = v C + 0.2v to v + C 0.1v l 500 2600 m v input offset voltage match (channel-to-channel) v cm = v C + 0.2v, v + C 0.1v (note 5) l 850 4000 m v i b input bias current v cm = v + C 0.1v l 0 1.4 2.8 m a v cm = v C + 0.2v l C 2.8 C 1.4 0 m a d i b input bias current shift v cm = v C + 0.2v to v + C 0.1v l 2.8 5.6 m a input bias current match (channel-to-channel) v cm = v + C 0.1v (note 5) l 75 1120 na v cm = v C + 0.2v (note 5) l 75 1120 na i os input offset current v cm = v + C 0.1v l 60 560 na v cm = v C + 0.2v l 60 560 na d i os input offset current shift v cm = v C + 0.2v to v + C 0.1v l 120 1120 na a vol large-signal voltage gain v o = C 14.5v to 14.5v, r l = 10k l 500 5000 v/mv v o = C 10v to 10v, r l = 2k l 250 1800 v/mv channel separation v o = C 10v to 10v, r l = 2k l 110 124 db cmrr common mode rejection ratio v cm = v C + 0.2v to v + C 0.1v l 81 96 db cmrr match (channel-to-channel) (note 5) v cm = v C + 0.2v to v + C 0.1v l 77 95 db psrr power supply rejection ratio v s = 5v to 15v l 80 93 db psrr match (channel-to-channel) (note 5) v s = 5v to 15v l 74 95 db v ol output voltage swing low (note 6) no load l 23 50 mv i sink = 5ma l 187 350 mv i sink = 25ma l 700 1400 mv v oh output voltage swing high (note 6) no load l 16 40 mv i source = 5ma l 300 600 mv i source = 25ma l 1500 3000 mv i sc short-circuit current l 27 54 ma i s supply current per amplifier l 5.3 7 ma gbw gain-bandwidth product (note 7) f = 100khz l 20 40 mhz sr slew rate a v = C 1, r l = open, v o = 10v, l 18 35 v/ m s measure at v o = 5v note 5: matching parameters are the difference between amplifiers a and d and between b and c on the lt1633; between the two amplifiers on the lt1632. note 6: output voltage swings are measured between the output and power supply rails. note 7: v s = 3v, v s = 15v gbw limit guaranteed by correlation to 5v tests. note 8: v s = 3v, v s = 5v slew rate limit guaranteed by correlation to 15v tests. note 9: minimum supply voltage is guaranteed by testing the change of v os to be less than 250 m v when the supply voltage is varied from 3v to 2.7v. the l denotes specifications that apply over the full operating temperature range. note 1: absolute maximum ratings are those values beyond which the life of a device may be impaired. note 2: a heat sink may be required to keep the junction temperature below the absolute maximum rating when the output is shorted indefinitely. note 3: this parameter is not 100% tested. note 4: the lt1632c/lt1633c are guaranteed to meet specified performance from 0 c to 70 c and are designed, characterized and expected to meet these extended temperature limits, but are not tested at C40 c and 85 c. guaranteed i grade parts are available, consult factory.
8 lt1632/lt1633 sn1632 16323fs typical perfor m a n ce characteristics u w supply current vs supply voltage total supply votage (v) 04 supply current per amplifier (ma) 36 1630/31 g01 812 16 20 24 28 32 6.0 5.5 5.0 4.5 4.0 3.5 3.0 2.5 2.0 t a = 125 c t a = 55 c t a = 25 c temperature ( c) ?0 input bias current ( a) 2.8 2.0 1.2 0.4 0 0.4 1.2 2.0 2.8 70 1632/33 g04 ?0 10 40 ?5 85 ? 25 55 100 v s = 5v, 0v v cm = 0v v s = 15v v cm = 15v npn active pnp active v s = 15v v cm = 15v v s = 5v, 0v v cm = 5v temperature ( c) ?5 supply current per amplifier (ma) 0 1632/33 g02 50 ?5 25 6.0 5.5 5.0 4.5 4.0 3.5 3.0 2.5 50 75 125 100 v s = 15v v s = 5v, 0v supply current vs temperature input bias current vs temperature load current (ma) saturation voltage (v) 0.01 1 10 100 1632/33 g05 0.1 10 1 0.1 0.01 v s = 5v, 0v t a = 55 c t a = 125 c t a = 25 c output saturation voltage vs load current (output low) load current (ma) saturation voltage (v) 0.01 1 10 100 1632/33 g06 0.1 10 1 0.1 0.01 v s = 5v, 0v t a = 55 c t a = 125 c t a = 25 c output saturation voltage vs load current (output high) common mode voltage (v) ? input bias current ( a) 23456 1632/33 g03 ? 0 1 2.0 1.5 1.0 0.5 0 0.5 1.0 1.5 2.0 t a = 125 c t a = 55 c t a = 25 c v s = 5v, 0v input bias current vs common mode voltage v os distribution, v cm = 0v (pnp stage) v os distribution, v cm = 5v (npn stage) input offset voltage ( v) 1250 percent of units (%) 50 40 30 20 10 0 750 1632/33 g31 750 ?50 250 1250 v s = 5v, 0v v cm = 0v input offset voltage ( v) 1250 percent of units (%) 50 40 30 20 10 0 750 1632/33 g32 750 ?50 250 1250 v s = 5v, 0v v cm = 5v input offset voltage ( v) 1250 percent of units (%) 50 40 30 20 10 0 750 1632/33 g33 750 ?50 250 1250 v s = 5v, 0v d v os shift for v cm = 0v to 5v
9 lt1632/lt1633 sn1632 16323fs typical perfor m a n ce characteristics u w total supply voltage (v) 1 0 change in offset voltage ( m v) 100 200 300 400 23 4 5 1632/33 g07 500 600 t a = 125 c t a = 55 c t a = 25 c frequency (hz) 1 noise voltage (nv/ ? hz) 10 100 1000 11632/33 g09 70 60 50 40 30 20 10 0 v s = 5v, 0v v cm = 2.5v pnp active v cm = 4.25v npn active noise voltage spectrum minimum supply voltage 0.1hz to 10hz output voltage noise gain bandwidth and phase margin vs supply voltage total supply voltage (v) 0 gain bandwidth (mhz) phase margin (deg) 5 10 15 20 1632/33 g14 25 120 105 90 75 60 45 30 15 0 80 70 60 50 40 30 20 10 0 30 phase margin v cm = v s /2 gain bandwidth gain and phase vs frequency frequency (hz) 40 common mode rejection ratio (db) 60 80 70 100 120 30 50 90 110 1k 100k 1m 10m 1632/33 g12 20 10k v s = 15v v s = 5v, 0v cmrr vs frequency psrr vs frequency frequency (hz) power supply rejection ratio (db) 100 90 80 70 60 50 40 30 20 10 0 1k 100k 1m 10m 1632/33 g13 10k v s = 15v positive supply negative supply channel separation vs frequency frequency (hz) 10 channel separation (db) 100 1k 10k 100k 1m 1632/33 g15 ?0 ?0 ?0 ?0 ?0 ?0 100 110 120 130 140 v s = 15v v out = 10v p-p r l = 2k noise current spectrum frequency (hz) 1 8 current noise (pa/ ? hz) 10 12 14 16 10 100 1000 1632/33 g10 6 4 2 0 18 20 v s = 5v, 0v v cm = 2.5v pnp active v cm = 4.25v npn active frequency (mhz) voltage gain (db) phase shift (deg) 80 70 60 50 40 30 20 10 0 ?0 ?0 225 180 135 90 45 0 ?5 ?0 135 180 225 0.01 1 10 100 1632/33 g11 0.1 phase gain r l = 1k v s = 3v, 0v v s = 15v time (1sec/div) output voltage (200nv/div) 1632/33 g08 v s = 5v, 0v v cm = v s /2
10 lt1632/lt1633 sn1632 16323fs typical perfor m a n ce characteristics u w output step vs settling time to 0.01% settling time ( m s) 0 0.25 ?0 output step (v) ? ? ? 0 10 4 0.50 0.75 1.00 1632/33 g18 ? 6 8 2 v s = 15v noninverting inverting inverting noninverting capacitive load (pf) 1 overshoot (%) 10 100 1000 1632/33 g16 90 80 70 60 50 40 30 v s = 5v, 0v a v = 1 r l = 1k capacitive load handling output voltage (v) ? ? ? ? ? input voltage ( v) 200 150 100 50 0 ?0 100 150 200 3 1632/33 g21 1 0246 57 v s = 15v r l = 100 output voltage (v) 0 input voltage ( m v) 3 5 1632/33 g20 12 4 20 15 10 5 0 ? ?0 ?5 ?0 6 v s = 5v, 0v r l = 1k r l = 10k open-loop gain open-loop gain open-loop gain output voltage (v) ?0 15 input voltage ( m v) 0 10 20 1632/33 g19 ?0 ?0 ?0 5 05 10 15 20 ? 5 ?5 15 v s = 15v r l = 1k r l = 10k time after power-up (sec) 0 change in offset voltage ( m v) 100 0 100 200 ?00 400 500 60 100 160 1632/33 g22 20 40 80 120 140 n8 package, v s = 5v, 0v s8 package, v s = 5v, 0v n8 package, v s = 15v lt1633cs, v s = 5v, 0v s8 package, v s = 15v lt1633cs, v s = 15v frequency (khz) thd + noise (%) 1 0.1 0.01 0.001 0.0001 0.1 10 100 1632/33 g23 1 v s = 3v, 0v a v = 1 v in = 2v p-p r l = 10k v s = 5v, 0v a v = 1 v s = 5v, 0v and 3v, 0v a v = 1 total harmonic distortion + noise vs frequency total supply voltage (v) 0 slew rate (v/ s) 812 20 2832 416 24 36 1632/33 g17 55 50 45 40 35 30 25 20 rising edge falling edge v out = 80% of v s a v = 1 slew rate vs supply voltage frequency (khz) 1 output voltage swing (v p-p ) 10 100 1000 1630/31 g24 5 4 3 2 1 0 a v = 1 v s = 5v, 0v a v = 1 maximum undistorted output signal vs frequency warm-up drift vs time
11 lt1632/lt1633 sn1632 16323fs typical perfor m a n ce characteristics u w 5v large-signal response 1632/33 g26 v s = 5v, 0v a v = 1 r l = 1k 5v small-signal response 163233 g25 v s = 5v, 0v a v = 1 r l = 1k harmonic distortion vs frequency frequency (khz) 100 harmonic distortion (dbc) 0 ?0 ?0 ?0 ?0 100 1000 2000 1632/33 g29 200 500 v s = 5v, 0v a v = 1 v in = 2v p-p r l = 150 r l = 1k 2nd 3rd 2nd 3rd harmonic distortion vs frequency 15v large-signal response 1632/33 g27 v s = 15v a v = 1 r l = 1k 15v small-signal response frequency (khz) 100 harmonic distortion (dbc) 0 ?0 ?0 ?0 ?0 100 1000 2000 1632/33 g30 1000 200 500 2nd 3rd 3rd v s = 5v, 0v a v = 1 v in = 2v p-p r l = 150 r l = 1k 2nd 1632/33 g28 v s = 15v a v = 1 r l = 1k applicatio n s i n for m atio n wu u u rail-to-rail input and output the lt1632/lt1633 are fully functional for an input and output signal range from the negative supply to the posi- tive supply. figure 1 shows a simplified schematic of the amplifier. the input stage consists of two differential amplifiers, a pnp stage q1/q2 and an npn stage q3/q4 that are active over different ranges of input common mode voltage. the pnp differential input pair is active for input common mode voltages v cm between the negative supply to approximately 1.5v below the positive supply. as v cm moves closer toward the positive supply, the transistor q5 will steer the tail current i 1 to the current mirror q6/q7, activating the npn differential pair and the pnp pair becomes inactive for the rest of the input com- mon mode range up to the positive supply. the output is configured with a pair of complementary common emitter stages q14/q15 that enables the output to swing from rail to rail. these devices are fabricated on linear technologys proprietary complementary bipolar process to ensure similar dc and ac characteristics. capacitors c1 and c2 form local feedback loops that lower the output impedance at high frequencies. power dissipation the lt1632/lt1633 amplifiers combine high speed and large output current drive in a small package. because the
12 lt1632/lt1633 sn1632 16323fs applicatio n s i n for m atio n wu u u amplifiers operate over a very wide supply range, it is possible to exceed the maximum junction temperature of 150 c in plastic packages under certain conditions. junc- tion temperature t j is calculated from the ambient tem- perature t a and power dissipation p d as follows: lt1632cn8: t j = t a + (p d ? 130 c/w) lt1632cs8: t j = t a + (p d ? 190 c/w) lt1633cs: t j = t a + (p d ? 150 c/w) the power dissipation in the ic is the function of the supply voltage, output voltage and load resistance. for a given supply voltage, the worst-case power dissipation p dmax occurs at the maximum supply current and when the output voltage is at half of either supply voltage (or the maximum swing if less than 1/2 supply voltage). there- fore p dmax is given by: p dmax = (v s ? i smax ) + (v s /2) 2 /r l to ensure that the lt1632/lt1633 are used properly, calculate the worst-case power dissipation, use the ther- mal resistance for a chosen package and its maximum junction temperature to derive the maximum ambient temperature. example: an lt1632cs8 operating on 15v supplies and driving a 500 w , the worst-case power dissipation per amplifier is given by: p dmax = (30v ? 5.6ma) + (15v C 7.5v)(7.5/500) = 0.168 + 0.113 = 0.281w if both amplifiers are loaded simultaneously, then the total power dissipation is 0.562w. the so-8 package has a junction-to-ambient thermal resistance of 190 c/w in still air. therefore, the maximum ambient temperature that the part is allowed to operate is: t a = t j C (p dmax ? 190 c/w) t a = 150 c C (0.562w ? 190 c/w) = 43 c for a higher operating temperature, lower the supply voltage or use the dip package part. input offset voltage the offset voltage changes depending upon which input stage is active, and the maximum offset voltages are trimmed to less than 1350 m v. to maintain the precision characteristics of the amplifier, the change of v os over the entire input common mode range (cmrr) is guaranteed to be less than 1500 m v on a single 5v supply. input bias current the input bias current polarity depends on the input common mode voltage. when the pnp differential pair is active, the input bias currents flow out of the input pins. q4 q6 v bias d7 d5 +in d2 q3 q7 q1 i 1 i 2 + + q9 q2 d4 d1 d3 ?n out v v + d8 d6 q5 q12 q8 q14 1632/33 f01 c1 r1 r6 225 r7 225 r3 v c c r4 r5 c2 r2 q11 q13 q15 buffer and output bias figure 1. lt1632 simplified schematic diagram
13 lt1632/lt1633 sn1632 16323fs applicatio n s i n for m atio n wu u u they flow in the opposite direction when the npn input stage is active. the offset voltage error due to input bias currents can be minimized by equalizing the noninverting and inverting input source impedance. output the outputs of the lt1632/lt1633 can deliver large load currents; the short-circuit current limit is 70ma. take care to keep the junction temperature of the ic below the absolute maximum rating of 150 c (refer to the power dissipation section). the output of these amplifiers have reverse-biased diodes to each supply. if the output is forced beyond either supply, unlimited current will flow through these diodes. if the current is transient and limited to several hundred ma, no damage to the part will occur. overdrive protection to prevent the output from reversing polarity when the input voltage exceeds the power supplies, two pairs of crossing diodes d1 to d4 are employed. when the input voltage exceeds either power supply by approximately 700mv, d1/d2 or d3/d4 will turn on, forcing the output to the proper polarity. for this phase reversal protection to work properly, the input current must be limited to less than 5ma. if the amplifier is to be severely overdriven, an external resistor should be used to limit the overdrive current. the lt1632/lt1633s input stages are also protected against large differential input voltages by a pair of back- to-back diodes d5/d8. when a differential voltage of more than 1.4v is applied to the inputs, these diodes will turn on, preventing the emitter-base breakdown of the input transistors. the current in d5/d8 should be limited to less than 10ma. internal 225 w resistors r6 and r7 will limit the input current for differential input signals of 4.5v or less. for larger input levels, a resistor in series with either or both inputs should be used to limit the current. worst-case differential input voltage usually occurs when the output is shorted to ground. in addition, the amplifier is protected against esd strikes up to 3kv on all pins. capacitive load the lt1632/lt1633 are wideband amplifiers that can drive capacitive loads up to 200pf on 15v supplies in a unity-gain configuration. on a 3v supply, the capacitive load should be kept to less than 100pf. when there is a need to drive larger capacitive loads, a resistor of 20 w to 50 w should be connected between the output and the capacitive load. the feedback should still be taken from the output so that the resistor isolates the capacitive load to ensure stability. feedback components the low input bias currents of the lt1632/lt1633 make it possible to use the high value feedback resistors to set the gain. however, care must be taken to ensure that the pole formed by the feedback resistors and the total capacitance at the inverting input does not degrade stability. for instance, the lt1632/lt1633 in a noninverting gain of 2, set with two 20k resistors, will probably oscillate with 10pf total input capacitance (5pf input capacitance and 5pf board capacitance). the amplifier has a 6mhz cross- ing frequency and a 55 phase margin at 6db of gain. the feedback resistors and the total input capacitance form a pole at 1.6mhz that induces a phase shift of 75 at 5mhz! the solution is simple: either lower the value of the resistors or add a feedback capacitor of 10pf or more. typical applicatio n s u single supply, 40db gain, 550khz instrumentation amplifier an instrumentation amplifier with a rail-to-rail output swing, operating from a 3v supply can be constructed with the lt1632 as shown in the first page of this data sheet. the amplifier has a nominal gain of 100, which can be adjusted with resistor r5. the dc output level is set by the difference of the two inputs multiplied by the gain of 100. the voltage gain and the dc output level can be expressed as follows:
14 lt1632/lt1633 sn1632 16323fs figure 4. rf amplifier control biasing and dc restoration typical applicatio n s u a r r r r rr r vvva v out in in v =++ + ? ? ? ? =- ? ? ? ? +- 4 3 1 2 1 32 5 common mode range can be calculated by the following equations: lower v v a r r v upper v v a r r vv where v cml out v cmh out v s s limit common mode input voltage limit common mode input voltage is supply voltage. = ? ? ? ? + ? ? = ? ? ? ? +- () ? ? 2 5 01 10 11 2 5 015 10 11 . . . . . . for example, the common mode range is from 0.15v to 2.65v if the output is set at one half of the 3v supply. the common mode rejection is greater than 110db at 100hz when trimmed with resistor r1. the amplifier has a bandwidth of 550khz. single supply, 400khz, 4th order butterworth filter the circuit shown in figure 2 makes use of the low voltage operation and the wide bandwidth of the lt1632 to create a 400khz 4th order lowpass filter with a single supply. the amplifiers are configured in the inverting mode to mini- mize common mode induced distortion and the output can swing rail-to-rail for the maximum dynamic range. figure 3 displays the frequency response of the filter. stopband attenuation is greater than 85db at 10mhz. + a1 1/2 lt1632 v out 1632/33 f04 5v 5v hp-msa0785 hp-msa0785 r3 10k l1 220 h c5 0.01 f l2 220 h q1 2n3906 q2 2n3906 c6 0.01 f r5 50 r1 10 r2 453 r4 10 c3 1500pf + a2 1/2 lt1632 c4 1500pf c2 1500pf c1 0.01 f v in l4 3.9 h l3 3.9 h + + + rf1 rf2 figure 2. single supply, 400khz, 4th order butterworth filter frequency (hz) 0.1k gain (db) 1k 10k 100k 1m 10m 1632/33 f03 10 0 ?0 ?0 ?0 ?0 ?0 ?0 ?0 ?0 ?0 v s = 3v, 0v v in = 2.5v p-p figure 3. frequency response + 1/2 lt1632 2.32k v in v s /2 v out 1632/33 f02 220pf 2.32k 6.65k + 1/2 lt1632 2.74k 22pf 470pf 5.62k 2.74k 47pf with a 2.25v p-p , 100khz input signal on a 3v supply, the filter has harmonic distortion of less than C 87dbc. rf amplifier control biasing and dc restoration taking advantage of the rail-to-rail input and output, and the large output current capability of the lt1632, the circuit shown in figure 4 provides precise bias current for the rf amplifiers and restores the dc output level. to ensure optimum performance of an rf amplifier, its bias point must be accurate and stable over the operating
15 lt1632/lt1633 sn1632 16323fs information furnished by linear technology corporation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no represen- tation that the interconnection of its circuits as described herein will not infringe on existing patent rights. s package 14-lead plastic small outline (narrow 0.150) (ltc dwg # 05-08-1610) temperature range. the op amp a1 combined with q1, q2, r1, r2 and r3 establishes two current sources of 21.5ma to bias rf1 and rf2 amplifiers. the current of q1, is determined by the voltage across r2 over r1, which is then replicated in q2. these current sources are stable and precise over temperature and have a low dissipated power due to a low voltage drop between their terminals. the amplifier a2 is used to restore the dc level at the output. with a large output current of the lt1632, the output can be set at 1.5v dc on 5v supply and 50 w load. this circuit has a C 3db bandwidth from 2mhz to 2ghz and a power gain of 25db. typical applicatio n s u 0.016 ?0.050 0.406 ?1.270 0.010 ?0.020 (0.254 ?0.508) 45 0 ?8 typ 0.008 ?0.010 (0.203 ?0.254) s14 0695 1 2 3 4 0.150 ?0.157** (3.810 ?3.988) 14 13 0.337 ?0.344* (8.560 ?8.738) 0.228 ?0.244 (5.791 ?6.197) 12 11 10 9 5 6 7 8 0.053 ?0.069 (1.346 ?1.752) 0.014 ?0.019 (0.355 ?0.483) 0.004 ?0.010 (0.101 ?0.254) 0.050 (1.270) typ dimension does not include mold flash. mold flash shall not exceed 0.006" (0.152mm) per side dimension does not include interlead flash. interlead flash shall not exceed 0.010" (0.254mm) per side * ** package descriptio n u dimensions in inches (millimeters) unless otherwise noted. n8 package 8-lead pdip (narrow 0.300) (ltc dwg # 05-08-1510) n8 1197 0.009 ?0.015 (0.229 ?0.381) 0.300 ?0.325 (7.620 ?8.255) 0.325 +0.035 0.015 +0.889 0.381 8.255 () 0.100 0.010 (2.540 0.254) 0.065 (1.651) typ 0.045 ?0.065 (1.143 ?1.651) 0.130 0.005 (3.302 0.127) 0.020 (0.508) min 0.018 0.003 (0.457 0.076) 0.125 (3.175) min 12 3 4 87 6 5 0.255 0.015* (6.477 0.381) 0.400* (10.160) max *these dimensions do not include mold flash or protrusions. mold flash or protrusions shall not exceed 0.010 inch (0.254mm) s8 package 8-lead plastic small outline (narrow 0.150) (ltc dwg # 05-08-1610) so8 0996 0.016 ?0.050 0.406 ?1.270 0.010 ?0.020 (0.254 ?0.508) 45 0 ?8 typ 0.008 ?0.010 (0.203 ?0.254) 0.053 ?0.069 (1.346 ?1.752) 0.014 ?0.019 (0.355 ?0.483) 0.004 ?0.010 (0.101 ?0.254) 0.050 (1.270) typ 1 2 3 4 0.150 ?0.157** (3.810 ?3.988) 8 7 6 5 0.189 ?0.197* (4.801 ?5.004) 0.228 ?0.244 (5.791 ?6.197) dimension does not include mold flash. mold flash shall not exceed 0.006" (0.152mm) per side dimension does not include interlead flash. interlead flash shall not exceed 0.010" (0.254mm) per side * **
16 lt1632/lt1633 sn1632 16323fs lt/tp 0998 4k ? printed in usa ? linear technology corporation 1998 linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 l fax: (408) 434-0507 l www.linear-tech.com typical applicatio n u + a2 1/2 lt1632 v in v out 1632/33 f05 5v 5v r2 1k r9 1k r8 5k r11 10k r10 10k r6 1k r1 500 r5 1k r7 1k r 1.62k r 1.62k c 1000pf c 1000pf + a1 1/2 lt1632 c2 4.7 f c5 4.7 f c1 2.2 f figure 5. tunable q notch filter part number descripton comments lt1211/lt1212 dual/quad 14mhz, 7v/ m s, single supply precision op amps input common mode includes ground, 275 m v v os(max) , 6 m v/ c max drift, max supply current 1.8ma per op amp lt1213/lt1214 dual/quad 28mhz, 12v/ m s, single supply precision op amps input common mode includes ground, 275 m v v os(max) , 6 m v/ c max drift, max supply current 3.5ma per op amp lt1215/lt1216 dual/quad 23mhz, 50v/ m s, single supply precision op amps input common mode includes ground, 450 m v v os(max) , 6 m v/ c max drift, max supply current 6.6ma per op amp lt1498/lt1499 dual/quad 10mhz, 6v/ m s rail-to-rail input and output high dc accuracy, 475 m v v os(max) , 4 m v/ c max drift, c-load tm op amps max supply current 2.2ma per amp lt1630/lt1631 dual/quad 30mhz, 10v/ m s rail-to-rail input and output op amps high dc accuracy, 525 m v v os(max) , 70ma output current, max supply current 4.4ma per amp c-load is a trademark of linear technology corporation. related parts f rc rk cpf vv r rr v a o odc v = = = = + = = 1 2 162 1000 5 11 11 10 25 2 p . . () tunable q notch filter a single supply, tunable q notch filter as shown in figure 5 is built with lt1632 to maximize the output swing. the filter has a gain of 2, and the notch frequency (f o ) is set by the values of r and c. the resistors r10 and r11 set up the dc level at the output. the q factor can be adjusted by varying the value of r8. the higher value of r8 will decrease q as depicted in figure 6, because the output induces less of feedback to amplifier a2. the value of r7 should be equal or greater than r9 to prevent oscillation. if r8 is a short and r9 is larger than r7, then the positive feedback from the output will create phase inversion at the output of amplifier a2, which will lead to oscillation. frequency (khz) 40 20 0 ?0 ?0 gain (v out /v in )(db) 13632/33 f06 0 20 40 60 140 160 180 200 80 100 120 increasing r8 decreasing r8 figure 6. frequency response
operational amplifiers (op amps) home > products > signal conditioning > operational amplifiers (op amps) > precision amplifiers > lt1632 high speed amplifiers precision amplifiers zero drift amplifiers low noise amplifiers low power amplifiers low bias current amplifiers high output current amplifiers current feedback amplifiers current sense amplifiers programmable gain amplifiers differential amplifiers instrumentation amplifiers video functions if amplifiers / adc drivers search lt1632 - 45mhz, 45v/us, dual/quad rail-to-rail input and output precision op amps features gain-bandwidth product: 45mhz slew rate: 45v/s low supply current per amplifier: 4.3ma input common mode range includes both rails output swings rail-to-rail input offset voltage, rail-to-rail: 1350v max input offset current: 440na max input bias current: 2.2a max open-loop gain: 800v/mv min low input noise voltage: 12nv/rthz typ low distortion: ?92dbc at 100khz wide supply range: 2.7v to 15v large output drive current: 35ma min dual in 8-pin pdip and so packages typical application back to top order now request samples documentation datasheet lt1632 - 45mhz, 4 5 dual/quad rail - to - r and output precisi o lt magazine march 2005 - low - d sine wave oscillat o precise rms ampli t may 1998 low dist o to - rail op amps h a thd with 100khz s reliability data r290 reliability da t software and simulatio n lt1632 spice mo d pa g e 1 of 3 linear technolo gy - lt1632 - 45mhz, 45v/us, du al/quad rail-to-rail in p ut and out p ut... htt p ://www.linear.com/ p c/ p roductdetail. j s p ?navid=h0,c1,c1154,c1009,c1021,p1641
description the lt1632/lt1633 have excellent dc pr ecision over the full range of operation. input offset voltage is typically less than 400v and the minimum open-loop gain of 0.8 million into a 10k load virtually eliminates all gain error. common mode rejection is typically 83db over the full rail-to-rail input range when on a single 5v supply for excellent noninverting performance. the lt1632/lt1633 maintain their perform ance for supplies from 2.7v to 36v and are specified at 3v, 5v and 15v supplies. the inputs can be driven beyond the supplies without damage or phase reversal of the output. the output delivers load currents in excess of 35ma. the lt1632 is available in 8-pin pdip and so packages with the standard dual op amp pinout. the lt1633 features the standar d quad op amp configuration and is available in a 14-pin plastic so package. these devices can be used as plug-in replacements for many standar d op amps to improve input/output range and performance. packaging dip-8,so-8 order info part numbers ending in pbf are lead free . please contact ltc marketing for information on lead based finish parts. part numbers containing tr or trm are shipped in tape and reel or 500 unit mini tape and reel , respectively please refer to our general ordering information or the product datasheet for more details package variations and pricing * the usa list pricing shown is for budgetary use only, shown in united states dollars (fob usa per unit for the stated volume), and is subject to change. international prices may differ due to local duties, taxes, fees and exchange rates. for volume-specific price or delivery quotes, please contact your local linear technology sales office or authorized distributor . back to top back to top part number package pins temp price (1- 99) price (1k) * rohs data lt1632cn8 pdip 8 c $3.70 $3.05 view lt1632cn8#pbf pdip 8 c $3.70 $3.05 view lt1632cs8 so 8 c $3.90 $3.20 view lt1632cs8#pbf so 8 c $3.90 $3.20 view lt1632cs8#tr so 8 c $3.26 view lt1632cs8#trpbf so 8 c $3.26 view lt1632in8 pdip 8 i $4.44 $3.66 view lt1632in8#pbf pdip 8 i $4.44 $3.66 view lt1632is8 so 8 i $4.68 $3.84 view lt1632is8#pbf so 8 i $4.68 $3.84 view lt1632is8#tr so 8 i $3.90 view lt1632is8#trpbf so 8 i $3.90 view buy now request samples back to top pa g e 2 of 3 linear technolo gy - lt1632 - 45mhz, 45v/us, du al/quad rail-to-rail in p ut and out p ut... htt p ://www.linear.com/ p c/ p roductdetail. j s p ?navid=h0,c1,c1154,c1009,c1021,p1641
site help site map site index send us feedback ? 2007 linear technology | terms of use | privacy policy applications active filters rail-to-rail buffer amplifiers driving a/d converters low voltage signal processing battery-powered systems simulate linear technology offers several options for simulating our high performance operational amplifiers. download the spice model for the lt1632 (or right click and select "save target as" to save the file to disk) download spice models for the complete collection of ltc op amps ltspice / switchercad iii is a powerful free circuit simulator and schematic capture program. included in this download are ltspice, macro models for 80% of linear technology's switching regulators, over 200 op amp models, as well as resistors, transistors and mosfet models. download it now! back to top back to top pa g e 3 of 3 linear technolo gy - lt1632 - 45mhz, 45v/us, du al/quad rail-to-rail in p ut and out p ut... htt p ://www.linear.com/ p c/ p roductdetail. j s p ?navid=h0,c1,c1154,c1009,c1021,p1641

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